Issue 
A&A
Volume 587, March 2016



Article Number  A143  
Number of page(s)  8  
Section  Astronomical instrumentation  
DOI  https://doi.org/10.1051/00046361/201526063  
Published online  03 March 2016 
Calibration of mixedpolarization interferometric observations
Tools for the reduction of interferometric data from elements with linear and circular polarization receivers
^{1} Department of Earth and Space Sciences, Chalmers University of Technology, Onsala Space Observatory, 43992 Onsala, Sweden
email: mivan@chalmers.se
^{2} MaxPlanckInstitut für Radioastronomie, Auf dem Hügel 69, 53121 Bonn, Germany
Received: 10 March 2015
Accepted: 25 October 2015
Heterodyne receivers register the sky signal on either a circular polarization basis (where it is split into lefthand and righthand circular polarization) or a linear polarization basis (where it is split into horizontal and vertical linear polarization). We study the problem of interferometric observations performed with telescopes that observe on different polarization bases, hence producing visibilities that we call “mixed basis” (i.e., linear in one telescope and circular in the other). We present novel algorithms for the proper calibration and treatment of such interferometric observations and test our algorithms with both simulations and real data. The use of our algorithms will be important for the optimum calibration of forthcoming observations with the Atacama Large Mm/submm Array (ALMA) in verylongbaseline interferometry (VLBI) mode. Our algorithms will also allow us to optimally calibrate future VLBI observations at very high data rates (i.e., wide bandwidths), where linearpolarization feeds will be preferable at some stations, to overcome the polarimetric limitations due to the use of quarterwave plates.
Key words: instrumentation: interferometers / techniques: interferometric / techniques: polarimetric
© ESO, 2016
1. Introduction
Most heterodyne receivers record signals on a genuine linear basis. The receiver’s front end can be understood as two orthogonal dipoles, one horizontal (the Xaxis) and one vertical (the Yaxis), in the frame of the antenna mount (although there could also be a generic rotation of the XY plane on a third antenna axis, parallel to the source direction). The Atacama Large Mm/submm Array (ALMA) is a good example of an interferometer that uses linearfeed polarization receivers (e.g., Rudolf et al. 2007).
However, verylongbaseline interferometry (VLBI) observations involve baselines that are so long that the parallactic angle ψ of two antennas pointing to the same source can be quite different (assuming that the mounts of the antennas are altazimuthal). This orientation issue in VLBI can cause many problems if the signals are recorded on a linear polarization basis since the gain and polarization solutions are coupled in this case (Sault et al. 1996). Hence, the amplitude calibration must be known before any ψ correction can be applied. Given that it is desirable to apply the ψ correction as early as possible to prevent its aggregation into more critical phasecalibration steps, such as global fringefitting (Schwab & Cotton 1983) and phase referencing (Beasley & Conway 1995), the use of linearpolarization feeds in VLBI does not seem to be a practical choice.
Nevertheless, if the signals are recorded on a circular polarization basis (i.e., righthand, RCP, and lefthand, LCP, circular polarizations), the gain and polarization solutions are decoupled through the variation of ψ (Sault et al. 1996). In this R/L basis, the ψ correction becomes (to a firstorder approximation) a mere phase addition to RCP and LCP so there is no need to have either similar T_{sys} or known amplitude correction factors in the initial phase calibration. The ψ correction on this basis commutes with the gain calibration (both in amplitude and phase). In addition, if either of the channels (RCP or LCP) fails to be recorded (or is of bad quality), it is still possible to use the other channel for the science analysis (as long as the observed sources do not have circular polarization). This is not possible if the data are being observed on the X/Y basis since, in this case, both channels will always be needed for the ψ correction.
Circular polarization receivers can be built by just adding a quarterwave plate (or an equivalent device) at the front end of the receiver so that the incoming circular polarization is converted into linear and then detected by the dipoles (e.g., Marrone & Rao 2008). There are, however, some disadvantages to the use of these polarizers. The purity of the polarization is usually lower (there is more polarization leakage between the channels) and the effective bandwidth is also narrower. Quarterwave plates are designed to be optimum at a given frequency, but their performance degrades as the signal frequency departs from that used in the quarterwave plate design. These disadvantages make linear polarizers the optimum choice for interferometers with wideband receivers and high polarization purity, like ALMA and the SKA. For instance, most of the stations of the Global MmVLBI Array (GMVA), which use circular polarizers at 86 GHz, suffer from polarization leakages as high as 2−6% (MartíVidal et al. 2012); the reported leakage of the circular polarizers at the SubMillimeter Array (SMA) can also reach values up to 4% (Marrone & Rao 2008). In contrast, the leakage from the linear polarizers at ALMA reach amplitudes of ~1% (e.g., Rudolf et al. 2007).
It is possible to find the situation where two stations with different types of receivers (linear and circular) have to become part of the same interferometer. A good example is the phased ALMA used in VLBI mode. As we have already noted, ALMA uses receivers that record the signal on a linear (X/Y) basis, whereas VLBI stations mostly record the signals on a circular (R/L) basis. As a consequence, when the phased ALMA is used as a VLBI station, the visibilities between ALMA and the other VLBI antennas will be correlated on a mixed polarization basis (i.e., linear for ALMA, circular for the other stations). These visibilities have to be properly calibrated and converted to a pure circular basis before any further analysis can be performed.
An alternative approach to the mixedpolarization correlation would be to convert the ALMA data streams to an R/L basis before the correlation. However, neither the phase (and delay) offset(s) between X and Y nor the difference in the X/Y amplitude gains (and their time evolution) are known at the correlation stage. All these quantities are needed for an optimal polarization conversion. Basically, a gain offset between X and Y translates into a combination of gainlike and leakagelike effects in R/L, whose calibration is more complicated than that of a simple phase/amplitude gain (the leakage and phase terms interact in the fit in a nontrivial way, dependent on source structure and parallactic angle coverage, e.g., Cotton 1993; Sault et al. 1996). Hence, a blind X/Y to R/L conversion at the correlation stage, with no preliminary phase and amplitude corrections, will be far from optimal.
In this paper, we study the problem of how to calibrate and deal with visibilities using mixed polarization. In the next section, we describe the algorithms for the calibration of mixedpolarization visibilities related to a phased array with linearfeed receivers (e.g., ALMA) and related to a single station with linearfeed receivers (e.g., a VLBI station with no quarterwave plate). In Sect. 4, we present our software, where these algorithms are implemented. In Sect. 5, we test the performance of our algorithms with realistic simulations. In Sect. 6, we present the results of the calibration of real VLBI observations on mixedpolarization basis. In Sect. 7, we summarize our conclusions.
2. RIME formalism for polarimetry
We will make use of the formalism of the Radio Interferometer Measurement Equation (RIME, e.g., Hamaker et al. 1996). The RIME provides an abstraction of polarization basis (e.g., circular or linear) in a convenient mathematical framework in which the basis choice does not propagate explicitly in the full algebra for the interferometer response (Hamaker et al. 1996; Sault et al. 1996). Smirnov (2011a) makes use of this abstraction for a convenient formulation of the calibration problem on different polarization bases, and the problem of calibration/conversion from one basis to the other in a direct and elegant way.
In the following lines, we briefly summarize some of the results by Smirnov (2011a,b) that will be used in this paper. We refer the reader to the original publications by Smirnov, for a more detailed discussion. We will use the the ⊙ symbol to refer to the circular polarization basis and the + symbol to refer to the linear polarization.
The parameters x and y are two orthonormal vectors on the plane perpendicular to the wave propagation; e_{x} and e_{y} are the electricfield components of the source signal in the x and y directions, respectively. From e_{x} and e_{y} we can compute the electric field on a circular polarization basis. The conversion is straightforward, (1)
where r and l represent the righthand and lefthand circular polarizations, respectively, and j is the imaginary unit. For a given brightness distribution on the sky, we can define the crosscorrelation matrix in circular polarization basis, E_{⊙⊙}, for a given baseline and time, in the form (2)where e is the electric field at the first antenna and e′ is the electric field at the second antenna. This is the equivalent to the lefthand side of Eq. (7) in Smirnov (2011a), but for circularfeed receivers. For small fields of view, and if directiondependent effects in the antenna gains are neglected, this matrix is related to the Fourier transform of the brightness matrix defined in Smirnov (2011a). If the first antenna of the baseline is sensitive to linear polarization, the crosscorrelation matrix (i.e., E_{+⊙}) will instead be (3)We can define the matrix E_{⊙+} (i.e., linear polarization for the second antenna of the baseline and circular polarization for the first one) in a similar way. As is shown in Smirnov (2011a; see his Sect. 6.3), from Eq. (1) it follows that (4)where (5)The matrices C_{⊙+} and C_{+⊙} respectively convert polarizations from linear to circular and from circular to linear. In Smirnov (2011a) these matrices are called H (for hybrid); here we call them C (for conversion).
3. Calibration of mixedpolarization visibilities
The matrices C_{⊙+} and C_{+⊙} can convert the crosscorrelation matrix given on the basis of mixed polarizations (i.e., circularlinear or linearcircular) into a matrix given on the basis of pure circular polarization by applying it to just one side of the RIME. Hence, we can recover the crosscorrelation matrix in circularcircular polarization directly from the matrix given in mixed polarizations by applying a simple matrix product.
If we crosscorrelate the voltages registered at the receivers of two antennas sensitive to circular polarization, the resulting visibility matrix is (6)where V_{⊙⊙} is the visibility matrix with circular polarization in both antennas, v is the voltage in the first antenna, and v′ is the voltage of the second antenna. If the first antenna of the baseline is sensitive to linear polarization, the visibility matrix (i.e., V_{+⊙}) will instead be (7)We can define the matrix V_{⊙+} in a similar way. If J and J′ are the Jones matrices that fully calibrate the first and second antennas, respectively, of the baseline, then, using Eq. (8) in Smirnov (2011a), we can write (8)and (9)
where J_{+} and are the Jones matrices in the linear polarization basis and J_{⊙} and are the same matrices in the circular polarization basis. Applying Eq. (4), and keeping in mind that (AB)^{1} = B^{1}A^{1}, we have
These equations allow us to relate any visibility matrix given on a mixedpolarization basis with the crosscorrelation matrix given in a pure circularcircular basis. We note that if the product is applied to each integration time of the visibilities, there is no loss of signal coherence in the conversion.
3.1. Phased array with linear feeds
We let be the voltage registered by an antenna a at time t_{k} in a circular polarization basis. Antenna a may be, in our case, a standalone VLBI station with a circularpolarization feed. We let be the voltage at time t_{k} registered by the ith antenna of a phased array (which is named b) in a linear polarization basis. Since the phased signal of b at time t_{k} is the addition of the voltages of all the k phased antennas, the corresponding element of the visibility matrix V(a,b) (Smirnov 2011a) between the stations a and b is (10)That is, given that the correlation operator is linear, the visibility is equal to the sum of the correlations between antenna a and each individual antenna of the phased array. Taking into account all the polarization products, we can build the full visibility matrix in the same way, i.e., (11)In the absence of noise, and if the signals are perfectly calibrated, all the matrices V_{⊙+}(a,i) should be numerically equal (as long as the synthesized VLBI field of view is much smaller than the synthesized resolution of the phased array).
3.2. Effect of different antenna gains in the phased elements
The different antennas of the phased array are affected by slightly different gains, bandpass responses, and polarization leakage (Dterm factors). The observed visibility matrix is then related to the perfectlycalibrated visibility matrix V_{⊙+}(a,b) by the equation (12)where the calibration Jones matrix can be a function of frequency and time, and is related to all the calibration matrices (i.e., gain, bandpass, Dterms, etc.) of all the antennas in the phased array. Thanks to the linearity of the algebra, we can write (13)where antenna i is corrupted by an unknown overall gain . Given that the uncorrupted visibility V_{⊙+}(a,i) is assumed to be noisefree, perfectly calibrated, and independent of i, we can put V_{⊙+}(a,i) out of the sum and write (see Eq. (12)) (14)where ⟨...⟩ is the averaging operator over the antennas of the phased array. Our objective is to calculate the matrix of Eq. (12) using all the observables available. We let and be the bandpass gains of the ith antenna in the phased array for polarization X and Y, respectively. We let and be the phase and amplitude gains for the same antennas and polarizations. We also let α_{i} = exp(jΔφ_{i}) be the relative phasegain between X and Y for the same antenna, and and be the Dterms. The exact matrix for the full phased array becomes (15)The calibration matrix to be multiplied by the observed visibility matrix is the inverse of (see Eqs. (8), (9), and (12)).
3.3. Single station with linear feeds
If the station with a linearfeed receiver is a single dish, there is no standard way to compute the Jones matrices that calibrate/convert the mixedpolarization visibilities. In these cases, there are no linearlinear crosscorrelations from which the gains of the linearfeed receivers can be derived as we do in Eq. (14). Although the conversion with the hybrid matrix C is still possible, not correcting for the X and Y gains (and phase offsets) beforehand may lead to strong timedependent leakagelike effects in the circularcircular visibilities after the polarization conversion.
Fortunately, we can still use the information encoded in the mixedpolarization visibilities to perform a proper calibration. If V_{rr} and V_{ll} are the visibilities for the parallelhand circularcircular correlations, respectively RR and LL, then V_{rr}/V_{ll} = 1 regardless of the source structure (and provided that the source is not circularly polarized). We now suppose that the first antenna of the baseline observes with a linearfeed receiver. Each polarization channel, X and Y, is affected by different gains, B_{x} × G_{x} and B_{y} × G_{y}. However, if the polarization leakage is negligible the only quantity that is important for the calibration before the polarization conversion is the ratio of gains (i.e., the crosspolarization gain), B_{x} × G_{x}/ (B_{y} × G_{y}) = G_{x/y}, which can fortunately be derived easily. If we write V_{rr}/V_{ll} in terms of the mixedpolarization visibilities and the gain ratios, we can define a norm χ^{2} whose minimum determines the gain ratios, (16)where ω_{k} is the weight of the kth visibility matrix V^{k} and G_{k,R/L} is the ratio of gains for the second antenna (with a circularfeed receiver) of the baseline of that visibility. The term is related to the baselines that only involve antennas with circularfeed receivers, (17)where a_{k′} and b_{k′} are the first and second antennas in the baseline of visibility V^{k′}. In this leastsquares minimization, one of the antennas with circularfeed receivers has to be chosen to have a zero crosspolarization phase. This convention does not affect the calibration of the antenna with the linearfeed receiver. An advantage of this equation is that G_{x/y} and G_{k,R/L} are stable with time so we can apply long integration times to derive χ^{2} and use this approach even with weak sources. Once the χ^{2} is minimized as a function of G_{x/y} and G_{k,R/L}, we can calibrate and convert the mixedpolarization visibilities with the equation (18)This approach is conceptually similar to selfcalibration (Readhead & Wilkinson 1978), although the gain solutions are, in this case, independent of the inherent source structure if the source is not circularly polarized. We note that this algorithm can also be useful in some cases of observations involving a phased array with linearfeed receivers. For instance, if the crosscorrelations among the antennas of the phased array are not computed in fullpolarization mode, or if the parallactic angle coverage of the calibrators is not large, it may not be possible to calibrate the phase offset among the X and Y signals of the reference antenna in the phased array. In such cases the data can still be calibrated, although with no Dterm corrections. The approach to follow is to use Eqs. (12) and (13) (providing no phaseoffset information to the Jones matrix) and to then derive the X−Y phase offset from the mixedpolarization visibilities using Eq. (16).
4. Implementing the calibration/conversion of mixedpolarization visibilities
We have developed PolConvert, the calibration/conversion software that will be used in mmVLBI observations with the phased ALMA. The program applies the calibration and conversion equations given in the previous section for a phased array with linearfeed receivers. It reads the VLBI data in standard FITSIDI format^{1}; identifies the antenna(s) with linear feeds used in the observations; and converts the visibilities to a pure circular basis, saving the results in new FITSIDI files. In addition, the program can optionally read calibration tables from the Common Astronomy Software Applications (CASA) of the National Radio Astronomy Observatory (NRAO)^{2}, compute the Jones matrix (or matrices) for the phased array (Eq. (15)), and correct the VLBI visibilities (Eq. (12)) before the polarization conversion. Since the phased ALMA will provide the visibilities among ALMA antennas in addition to the phased signal for VLBI, the procedure to calibrate the VLBI observations will be to use the ALMAonly visibilities to derive the J_{i} calibration matrices of all ALMA antennas (Eq. (13)) and to provide these matrices to PolConvert to compute the total matrix (Eq. (15)). The CASA tables currently supported in PolConvert are (see Smirnov 2011a, for a definition): G Jones (i.e., gain and XY phase), B Jones (i.e., bandpass), K Jones (i.e., cross delay), and D Jones (i.e., polarization leakage). As noted above, all these tables are optional for the calibration applied before the conversion.
Several different linearpolarization VLBI stations can be corrected simultaneously, each with its own set of CASA calibration tables. However, if the station is a single dish, no tables can be provided (unless the user knows the gain ratios between the polarization channels of the antenna receivers), so no calibration is performed before the conversion. To optimize the polarization conversion of singledish antennas with linear receivers, we have implemented the algorithm described in Sect. 3.3 in a script called PolConvertST to be used in the Astronomical Image Processing (AIPS) environment of NRAO^{3} via the Python wrapper ParselTongue (Kettenis et al. 2006).
5. Testing the algorithm
5.1. Simulating phasedALMA observations
We have developed a simulator program to test the performance of the calibration/conversion algorithm implemented in PolConvert. Our simulation program, PolSimulate, generates synthetic data under realistic conditions. It takes into account noise from the receivers, signal quantization (amplitude and time), and corruption effects (atmosphere and receivers). The simulator creates a synthetic set of ALMAonly crosscorrelations (on a pure linear basis) and the corresponding phasedup data streams, which are crosscorrelated with simulated streams from a VLBI station with a circularfeed receiver. We then calibrate the ALMAonly visibilities following the usual ALMA reduction procedures to derive the gain matrices of all the ALMA antennas. Finally, we let PolConvert compute the Jones matrix for the phased ALMA, apply it to the VLBI fringes, and rewrite them on a pure circular basis. PolSimulate generates synthetic data following the steps summarized in the following lines:
 1.
Two random streams are created that simulate the signal from a source on R/L polarization basis. These streams can carry information on all four of the Stokes parameters, I, Q, U, and V.
Fig. 1 Bandpass and leakage gains for two of the simulated antennas. Lines are the gains used in the simulation; points are the gain values derived by CASA.
 2.
The R and L streams are phaserotated according to the parallactic angle of each scan in the simulation. The observations consist of a first scan of an amplitude calibrator (in this case the user can define Stokes I and V) and several scans of a polarization calibrator (the user can define all four Stokes parameters), equally spaced in time between transit and a maximum hour angle. The number of scans and hourangle coverage are given by the user in a configuration file.
 3.
Random noise (of amplitude determined by the configuration parameter T_{ant}/T_{sys}) is added to the R/L streams.
Fig. 2 VLBI visibility of the unpolarized amplitude calibrator. Top: mixedpolarization basis. Bottom: after conversion to pure circular basis. Bottom left: with no corrections based on the gains derived from the crosscorrelation of the ALMA antennas. Bottom right: after full calibration and conversion with PolConvert.
 4.
The noisefree R/L streams are converted to linear basis (altaz mounts assumed). The signal of each ALMA antenna is then computed as this signal plus uncorrelated noise (of amplitude similar to that in the previous step).
 5.
The signal from each ALMA antenna is corrupted with gain, bandpass, and leakage. These corrections are different for each antenna and polarization.
 6.
The (X/Y) signals of the ALMA antennas are crosscorrelated, and the result is saved in a measurement set (the data format used by CASA).
 7.
The phased signal (i.e., the sum of the signals from all the ALMA antennas) is crosscorrelated with the signal resulting from step 3. The result is saved in a FITSIDI file.
After the simulation, we calibrate the measurement set generated in step 6 using the standard calibration approach. The first scan is used to calibrate the bandpass and the gain (see step 2), whereas the rest of the observations are used to derive the crossdelay, XY phase offset, and Dterms.
We have simulated a phasedALMA mmVLBI dataset with the following parameters:

observing frequency: ν = 100 GHz;

bandwidth: Δν = 100 MHz;

number of ALMA antennas: N_{ant} = 10;

receiver noise: T_{ant}/T_{sys} = 0.1;

integration time: t_{int} = 1 s;

scan duration: t_{sc} = 25 s;

correlation channels: N_{chan} = 64;

number of scans: N_{sc} = 5;

declination of sources: δ = −60°;

maximum hour angle: H_{max} = 6 h;

maximum leakage (amp & phase): D_{max} = 3%;

maximum bandpass (amplitude): %;

maximum bandpass (phase): ;

maximum XY amplitude ratio: (G_{x}/G_{y})_{max} = 40%;

minimum period G_{1}: 0.25 cycles/Δν;

maximum period G_{1}: 2.00 cycles/Δν;

amplitude calib. (Jy): I = 1.0, Q = U = V = 0.0;

polarization calib. (Jy): I = 1.0, Q = 0.1, U = V = 0.0.
The magnitudes used for the gains are educated guesses based on our experience in the calibration of real ALMA data. Using these parameters, we obtained a measurement set (with the ALMAonly visibilities) and a FITSIDI file (with the VLBI visibilities). Some of the gains for the ALMA antennas are shown in Fig. 1. In all cases, the CASA estimates are very similar to the inputs used in the simulation. This gives us confidence on the reliability of PolSimulate. We note that the Stokes parameters of the polarization calibrator were left free in the calibration to make the calibration as realistic as possible. The results estimated by CASA when solving for the XY phase (i.e., running gaincal in mode “XYf+QU”) are Q = 0.0763 and U = 0.0089, not far from the values used in the simulation (i.e., Q = 0.1 and U = 0.0).
We show the visibilities of the amplitude calibrator in Fig. 2. The visibilities on a mixed basis (i.e., linear to circular) are shown at the top of the figure. Strong bandpass effects and phase offsets can be clearly seen. At bottom left, we show the visibilities converted in a circular basis, but without applying any calibration matrix. This figure illustrates the quality that we would obtain if the polarization conversion was applied either at the recording or at the correlation stage of the VLBI observations (i.e., before knowing the true gains of each individual ALMA antenna). There is a large polarization leakage left in the crosshand correlations (about 10% of the source flux density). Finally, at bottom right we show the visibilities resulting from the full calibration and conversion using PolConvert. All bandpass and leakage artifacts disappear and the resulting visibility is fully corrected; however, a residual phase in the parallelhand correlations can be clearly seen. This phase cannot be calibrated with the Jones matrix derived from the ALMAonly correlations since it is related to the time arrival of the signal to ALMA with respect to the other VLBI station. Obviously, such a time delay is not observable by ALMA alone and is hence transparent to the PolConvert calibration. However, this phase can be completely corrected with an ordinary fringefitting calibration after running PolConvert.
Fig. 3
VLBI visibility of the polarization calibrator (Q = 0.1;U = V = 0.0) after conversion to a pure circular basis. Left: for a parallactic angle of 0°; right: for a parallactic angle of 45°. 
Fig. 4
VLBI visibility matrix at 86 GHz between Onsala and Effelsberg in mixed polarization. Only one subband is shown. 
Fig. 5
VLBI visibility matrix at 86 GHz between Onsala and Effelsberg in circular polarization. Only one subband is shown. 
In Fig. 3, we show two scans of the polarization calibrator. On the left we show the visibility when the source is in transit (i.e., parallactic angle ψ = 0). The expected signal in RL and LR is recovered (i.e., the effect of Q translates into equal and realvalued correlations RL and LR). On the right, we show the results for the second scan of the polarization calibrator when the parallactic angle is close to ψ = 45°. Here, the original signal in Q is put into U (in the receiver’s frame of the antennas), so now RL and LR become purely imaginary and one is the complex conjugate of the other (RL with positive phase). This is exactly the behaviour that we see in the visibility calibrated and converted with PolConvert. The phases of RL and LR are equally spaced with respect to those of RR and LL.
6. Real VLBI observations
On 22 May 2014, we performed a fringetest VLBI observing session at 86 GHz using the Onsala 20 m telescope and the Effelsberg radio telescope. The recording rate was set to 1 Gbps, synthesizing a bandwidth of 256 MHz at each polarization channel (8 subbands of 32 MHz; two polarizations).
During part of this session, the staff at Onsala removed the quarterwave plate at the receiver’s front end, which sent the sky radiation directly into the receiving dipoles on a linear basis. Effelsberg continued data recording with no changes in its receiver, which means that during that time window Onsala was recording the signal in linear (X/Y) basis, while Effelsberg was recording in circular (R/L) basis. Unfortunately, only 10 s of integration time could be used in the correlation owing to problems in the lock system of the local oscilator at Onsala. During these 10 s, we were observing source OJ 287. a source with a negligible linear polarization. We crosscorrelated the data streams from Effelsberg and Onsala with version 2.3 of the program DiFX (Deller et al. 2007) using a frequency sampling of 128 channels per subband and an integration time of 0.25 s.
In Fig. 4, we show the amplitude fringes of an example subband of this observation (the second one) in delayrate space and mixedpolarization basis. Only weak detections are found in the correlation products. In Fig. 5, we show the fringes after applying the algorithm described in Sect. 3.3. This algorithm was applied to the raw data with no prior global fringefitting calibration, because it is not possible to apply it in a standard way to the mixedpolarization visibilities. This is the reason why we could not build the multiband delay to increase the signaltonoise ratio, S/N, of the detections when we applied the calibration algorithm described in Sect. 3.3.
Since there is only one baseline in these observations, we had to assume that the amplitude of the crosspolarization gain ratio was unity at Effelsberg. This assumption may have slightly degraded the calibration. If our array had had at least four antennas, we could have derived the true amplitude gain ratios for all the stations without any extra assumption.
Given the low S/N of our fringes due to the very short integration time, we had to derive the gain ratio for Onsala by averaging over all the frequency channels of the subband. Thus, unfortunately, we could not test the performance of the algorithm to calibrate the crosspolarization bandpass effects in the station with linearfeed receivers. In any case, the fringes after the calibration and conversion are very clear in the parallelhand correlations (RR and LL). The crosshand correlations (RL and LR) do not show detections, as should be the case for an unpolarized source.
7. Conclusions
Interferometric observations using elements with receivers of different polarization configurations may become common in the near future. The case of the phasedALMA project and its use in VLBI observations is a clear example. ALMA will observe in a linear polarization basis, whereas most of the other VLBI stations will observe in a circular polarization basis. In addition, future VLBI observations at very high data rates (hence wide bandwidths) may imply that it will not be optimum to use quarterwave plates at some stations, which would degrade the polarimetry quality of their observations. In such cases, these stations will also have to record their signals in linear polarization basis.
We have studied the problem of the calibration and proper polarimetry conversion of interferometric observations performed using mixed polarization (i.e., some antennas using linearfeed receivers and the rest using circularfeed receivers). We have developed PolConvert, a software for the calibration/conversion of VLBI mixedpolarization visibilities where the linearfeed station is a phased array. This program is especially designed for its use with ALMA mmVLBI visibilities. We have successfully tested PolConvert with realistic synthetic data. We have also developed an algorithm to calibrate and convert visibilities where the linearfeed station is a single dish. This algorithm can also be used to derive the crosspolarization phase offset of the reference antenna in the case of a phased array, if the parallactic angle coverage of the observations is not large enough to ensure a proper fullpolarization calibration. We have tested this algorithm with real stateoftheart VLBI observations at 86 GHz, performed in mixed polarization, between the Onsala and the Effelsberg radio telescopes. We have shown that it is possible to fully calibrate and convert the mixedpolarization VLBI visibilities, related either to the phased ALMA or to single stations with linearfeed receivers, using our calibration approaches.
Acknowledgments
I.M.V. thanks the COST Action MP1104 for travel support to the MPIfR.
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All Figures
Fig. 1 Bandpass and leakage gains for two of the simulated antennas. Lines are the gains used in the simulation; points are the gain values derived by CASA. 

In the text 
Fig. 2 VLBI visibility of the unpolarized amplitude calibrator. Top: mixedpolarization basis. Bottom: after conversion to pure circular basis. Bottom left: with no corrections based on the gains derived from the crosscorrelation of the ALMA antennas. Bottom right: after full calibration and conversion with PolConvert. 

In the text 
Fig. 3
VLBI visibility of the polarization calibrator (Q = 0.1;U = V = 0.0) after conversion to a pure circular basis. Left: for a parallactic angle of 0°; right: for a parallactic angle of 45°. 

In the text 
Fig. 4
VLBI visibility matrix at 86 GHz between Onsala and Effelsberg in mixed polarization. Only one subband is shown. 

In the text 
Fig. 5
VLBI visibility matrix at 86 GHz between Onsala and Effelsberg in circular polarization. Only one subband is shown. 

In the text 
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